Disturbance Observer-Based Anti-Shock Controller for Laser Beam Steering Systems

Abstract

This paper presents an approach for improving the robustness of tip-tilt controllers for fast-steering mirror (FSM)-based laser beam steering (LBS) systems in the presence of dynamic disturbances such as external shocks. To this end, we propose the addition of a disturbance observer (DOB)-based anti-shock controller in parallel to the original linear servo control loop to improve its control performance in the presence of external shocks. To increase the tip-tilt control performance against external shocks, the DOB-based control method, which is an improved control method for eliminating nonperiodic disturbances, is implemented in the original tip-tilt control system. The results indicate that the control error of the DOB-based anti-shock controller decreased, resulting in an efficient improvement in its disturbance-rejection performance.

1. Introduction

Fast-steering mirror (FSM)-based laser beam steering (LBS) systems are used extensively in various optical tracking control systems, such as line-of-sight stabilization, adaptive optics, and long-range laser communication [1,2,3]. Moreover, these systems are increasingly being mounted on mobile platforms such as spacecraft, satellites, airplanes, ships, and vehicles [4,5]. Therefore, the control precision of LBS systems must be improved to maintain the aiming point in the target plane while minimizing factors that cause jitter even under dynamic disturbances [6].

The robust design of FSM systems is typically approached from two perspectives. First, the design of structural parameters is considered to satisfy the control requirements of the target platform. FSM systems require flexible hinges as rigid elastic supports to achieve the desired structural stiffness and sustain driving forces for a certain range of strokes. Flexible hinges are designed and assembled to guarantee the required transmission resolution and accuracy, as well as to facilitate substantial rotation, because such hinges eliminate mechanical friction and sources of nonlinearity such as backlash, hysteresis, and static resistance [7,8]. In addition, flexible hinges do not require lubrication, have wide operating temperature ranges, and are more reliable than traditional bearings [9]. A flexible hinge should approximate a bearing connected to a mirror to ensure higher axial/torsional stiffness and lower rotational stiffness. However, the stiffness of flexible hinges in different directions is coupled, and therefore, axial/torsional stiffness cannot be considerably higher than rotational stiffness. In addition, reducing the rotational stiffness of a flexible hinge to expand its angular range inevitably reduces the axial/torsional stiffness. Second, to achieve high-precision control performance, it is necessary to design a control system with rapid response characteristics and strong disturbance-rejection control performance [10,11]. FSM systems typically use long-stroke voice coil actuators (VCAs) or high-actuation resolution piezoelectric (PZT) actuators, and their response, output force, and resolution are suitable for most applications. In particular, PZT actuators are more suitable than VCAs for use in applications that require higher actuation resolution and faster settling times. High-precision tip-tilt controllers for FSM systems are designed to ensure that the aforementioned VCAs or PZT actuators maintain an extremely small rotational position (under 10 μrad rms) in the presence of dynamic disturbances to satisfy the desired operating conditions. Therefore, several studies have been conducted to realize High-precision control performance. For instance, a method to eliminate the vibration effect of PZT actuators was proposed [12]. A notch filter was developed to effectively eliminate the main resonant mode of FSM systems [13]. In other studies, an input shape controller and an integral resonance controller were developed [14].

Primarily, two types of disturbances hinder the tip-tilt control of FSM systems: periodic and nonperiodic disturbances. First, periodic disturbances occur owing to the spinning of cooling fan units on the target platform. To eliminate periodic disturbances, repetitive controllers and adaptive feedforward cancellation (AFC) schemes have been applied [15,16]. Repetitive control technologies are the most widely used, either as internal or external model-based controllers [17]. Discrete-time repetitive controllers based on the internal model principle (IMP) have been synthesized and analyzed [18]. The most common approach is based on the IMP, which states that a model of the disturbance generation system must be included in the feedback system to realize disturbance cancellation. However, owing to hardware limitations of the servo loops used in FSM control systems, the classic AFC method cannot be used to precisely control rotational position. Second, nonperiodic disturbances occur when external shocks are applied to the target platform under operating conditions. Typically, the closed-loop bandwidth of the control system should be increased to ensure that the FSM system can eliminate the errors caused by such disturbances. However, doing so may reduce the stability of the FSM system owing to its increased sensitivity to high-frequency disturbance components. Consequently, a controller design that considers closed-loop bandwidth alone is inadequate [19,20]. Therefore, various studies have been conducted to design robust controls in the presence of external shocks, one of which is a robust control system that uses observer-based sliding mode control to manage shocks [21]. In addition, a direct measurement-based feedforward algorithm is proposed to suppress most of the theoretical external disturbances [22,23]. However, while the feedforward method works well in specific environments with low measurable noise, its implementation under more complex conditions is limited owing to the additional cost of another sensor.

To avoid the abovementioned problems, an emerging basic approach to suppressing disturbances can be used that estimates the influence of an external disturbance independently by using a disturbance observer (DOB) and then eliminating the perturbation by using the feedforward method. This feedforward method is called the DOB method [24,25]. It has been applied to several mobile devices with High-precision control systems, such as robot motion control, swing arm actuators in hard disk drives, VCAs in optical disk drives, and permanent magnet synchronous motor control [26,27,28]. To improve the control performance of the original control system for use in FSM systems, high open-loop gain is needed in the dynamic disturbance frequency domain to sufficiently attenuate disturbances. FSM systems commonly use high-bandwidth proportional-integral (PI) controllers owing to their robustness to modeling errors and simple implementation [29,30]. The addition of a DOB to the base controller significantly improves the disturbance attenuation performance because of its simplicity and suitability for real-time implementation [31,32].

In this study, we propose a more reliable anti-shock control algorithm by using a DOB to enhance the disturbance-suppression performance of FSM systems at low frequencies. The rest of this paper is organized as follows: Section 2 introduces the basic FSM control system. In Section 3, the DOB-based anti-shock controller is presented, and its performance is analyzed. Section 4 describes the experiments conducted to verify the proposed approach. Finally, our concluding remarks are presented in Section 5.

2. FSM Control System

2.1. Dynamic Characteristics of PZT Actuator

In the conventional approach to designing a High-precision FSM control system for tip-tilt control, a PZT actuator is used. The frequency response function (FRF) of an actuating plant is typically obtained using the sine-sweep method. Meanwhile, the real plant considered herein consists of a PZT actuator, a DC-DC converter-type amplifier, and a sensor amplifier. The dynamic specifications of the real plant indicate that its resonance frequency is 450.2 Hz. The DC sensitivity, voltage amplifier gain, and sensor amplifier gain are 168.3 µrad/V, 10 V/V, and 0.0059 V/µrad, respectively. Therefore, the real plant can be modeled as the following fifth-order transfer function [33]:

$$P\left(s\right)=\frac{6.08\times {10}^3{S}^3+7.09\times {10}^6{S}^2+5.85\times {10}^{10}S+6.27\times {10}^{13}}{S^5+8.95\times {10}^3{S}^4+7.49\times {10}^7{S}^3+1.50\times {10}^{11}{S}^2+5.21\times {10}^{14}S+3.73\times {10}^{17}}$$

(1)

The FRF of the real actuator and its modeling plant is illustrated in Figure 1. In addition, the dynamic characteristics of the real plant are summarized in

Table 1. Dynamic characteristics of real plant.

Specification	Value
Resonance frequency	450.2 Hz
5 Hz sensitivity	168.3 µrad/V
Gain of voltage amplifier	10 V/V
Gain of sensor amplifier	0.0059 V/µrad

.

The open-loop transfer function of a nominal plant is expressed as follows [34]:

$$\begin{array}{cc}\hfill P_n\left(s\right)& =\frac{K_{FSM}}{s^2+2\times \zeta {\omega }_{n}s+{{(\omega }_n)}^2},\hfill \\ & =\frac{K_{PZT}\times K_{Sensor}{\times K}_{Driver}}{s^2+2\times \zeta {\omega }_{n}s+{{(\omega }_n)}^2},\hfill \\ & =\frac{1.08\times {10}^3\times 0.0059\times 10}{s^2+2\left(0.0057\right)\left(450.2\right)s+{\left(450.2\right)}^2}\hfill \end{array}$$

(2)

where ζ and ω_n are the damping ratio and resonance frequency of the actuator, respectively. K_FSM denotes the DC gain of the nominal plant (i.e., FSM actuation system), which is composed of the DC gain of the PZT actuator, as well as the gains of the position sensor and PZT actuator driver.

The real plant and digital signal processor (DSP) platform used to evaluate the control performance of the FSM control system are depicted in Figure 2. A Scalexio AutoBox (dSPACE) is used to control the FSM control system. In addition, an S-340 piezo tip-tilt platform and an amplifier module (PI Ceramic GmbH, Lederhose, Germany) are used in the tip-tilt actuating platform.

2.2. Tip-Tilt Controller of FSM Control System

PI controllers are commonly used in real control systems for the tip-tilt control of FSM control systems. The tip-tilt controller is designed to achieve the designed gain margin, phase margin, crossover frequency, and loop gain. Although it is feasible to obtain a wider crossover frequency, the crossover frequency is limited by the sampling frequency of the DSP, feedback sensor signal, and other components. The open-loop transfer function of the designed PI controller for FSM control systems is illustrated in Figure 3, where the PI controller, crossover frequency, gain margin, phase margin, and loop gain are 91.1 Hz, 11.8 dB, 68.7°, and >30 dB, respectively. Moreover, the disturbance-rejection performance of the designed PI controller for FSM control systems is depicted in Figure 4. The transfer function of the PI controller is expressed as follows [35]:

$$C\left(s\right)=K_P+\frac{K_I}{s}=0.5+\frac{900}{s}$$

(3)

where K_P and K_I are the proportional and integral gains, respectively, and their values are 0.5 and 900, as determined using Equation (3).

3. Anti-Shock Controller for FSM System

3.1. Shock Specifications

As illustrated in Figure 5, a shock is defined as a half-sine pulse with 5 g acceleration and a duration of 10 ms. Unlike periodic disturbances, shocks exhibit nonperiodic characteristics. The aforementioned shock is applied to the system in the vertical direction of the optical bench on the platform so that it interacts as a factor that hinders the tip-tilt control of the FSM system.

3.2. DOB-Based Anti-Shock Controller

The design of the DOB-based anti-shock controller, which aims to compensate for disturbances, is simple to implement because a DOB-based controller can be obtained simply by attaching a DOB to the original FSM control system. Theoretically, the DOB can be designed as an extended structure in the feedback control loop. The DOB-based controller rejects disturbances by injecting a compensation value into the control input; this compensation value is equal to the difference between the commanded control input to the plant and the plant output filtered by the inverse of the nominal plant P_n(s), i.e., P_n⁻¹(s), as illustrated in Figure 6. However, because P_n⁻¹(s) generally contains pure differential terms, it is not often physically realizable. Therefore, it is common to use a Q filter in conjunction with P_n⁻¹(s). This Q filter typically has the characteristics of a low-pass filter (LPF) with a direct current (DC) gain of unity. In this study, a binomial Q filter is used as the LPF. The higher the filter order, the better the realized performance. A high-order filter could adversely affect the controller performance owing to phase lag. In addition, the bandwidth of the Q filter influences the system response. As the bandwidth of the Q filter increases, the speed of rejecting undesirable disturbances increases. Thus, the Q filter is important for securing the performance of the DOB. Figure 6 schematically illustrates the DOB-based anti-shock controller for FSM control systems. The Open-loop transfer function of a continuous system is expressed as follows [34]:

$$Q_{mn}\left(s\right)=\frac{{\sum }_{i=1}^n{a}_{mi}{\left(\tau s\right)}^i}{{\left(\tau s+1\right)}^m},$$

(4)

where τ is a time constant, a_mi denotes the binomial coefficients calculated as (m!/m − i)! i!, m is the denominator order, and n is the numerator order (m ≥ n). Generally, the robustness of the DOB improves as the denominator order increases. For example, if a Q₃₁ filter is used instead of a Q₂₀ filter, the robustness of the DOB system will improve. In addition, control system stability shares a trade-off relationship with the bandwidth of the Q filter. Therefore, the bandwidth of the Q filter must be selected experimentally to maximize the stability of the control system. For this reason, this study uses the binomial Q₂₀ and Q₃₁ filters in the proposed DOB-based controller for FSM systems, as illustrated in Figure 7. This is because the stability of the control system can be estimated from the residual control error signal (CES), which is the experimental result. The use of Q₂₀ and Q₃₁ filters effectively improves the disturbance-suppression performances of the FSM control system. Moreover, the disturbance-suppression performances of the FSM control system are effective in the low-frequency region with bandwidths of 15 and 30 Hz. The Open-loop transfer functions of the aforementioned Q₂₀ and Q₃₁ filters with bandwidths of 15 and 30 Hz are expressed as follows [34]:

$$Q_{20}\left(s\right)=\frac{1}{{\tau }^2{s}^2+2\tau s+1}=\frac{1}{4.6\times {10}^{-5}{s}^2+1.4\times {10}^{-2}s+1}[15\mathrm{H}\mathrm{z}]$$

(5)

$$Q_{20}\left(s\right)=\frac{1}{{\tau }^2{s}^2+2\tau s+1}=\frac{1}{1.2\times {10}^{-5}{s}^2+6.8\times {10}^{-3}s+1}[30\mathrm{H}\mathrm{z}]$$

(6)

$$Q_{31}\left(s\right)=\frac{3\tau s+1}{{\tau }^3{s}^3+{3\tau }^2{s}^2+3\tau s+1}=\frac{5.1\times {10}^{-2}s+1}{4.9\times {10}^{-6}{s}^3+8.7\times {10}^{-4}{s}^2+5.1\times {10}^{-2}s+1}[15\mathrm{H}\mathrm{z}]$$

(7)

$$Q_{31}\left(s\right)=\frac{3\tau s+1}{{\tau }^3{s}^3+{3\tau }^2{s}^2+3\tau s+1}=\frac{2.6\times {10}^{-2}s+1}{6.1\times {10}^{-7}{s}^3+2.2\times {10}^{-4}{s}^2+2.6\times {10}^{-2}s+1}[30\mathrm{H}\mathrm{z}]$$

(8)

As mentioned previously, the loop gain of the control system should be high in the frequency domain of dynamic disturbances. Therefore, the loop gain of the DOB-based anti-shock controller for FSM control systems is greater than that of the PI controller for the base tip-tilt controller. Moreover, the control loop gain is improved by increasing the bandwidth of the Q filter. The Open-loop transfer function of the overall DOB-based anti-shock controller for FSM control systems is illustrated in Figure 8, and it is expressed as follows [36]:

$$G_{DOB}(s)=\frac{\mathrm{C}\left(\mathrm{S}\right)P_n+1-(1-Q\left(s\right))}{(1-\mathrm{Q}\left(s\right))P_n},$$

(9)

where P_n(s) is the nominal plant, and Q(s) is the binomial Q filter. The Open-loop transfer function and sensitivity transfer function of the overall FSM control system with the modified DOB are presented in Figure 5 and Figure 6, respectively.

As illustrated in Figure 8 and Figure 9, the disturbance-rejection performance of the DOB-based anti-shock controller for FSM control systems improves as the denominator order of the Q filter increases. Furthermore, for the same denominator order (m) of the Q filter, an increase in the Q filter bandwidth improves the disturbance-rejection performance. For example, in the case of the FSM control system, the Open-loop gain of the Q₃₁ filter is superior to that of the Q₂₀ filter between 0 Hz and 70 Hz. If the denominator order of the filter is the same, then the Q filter with a bandwidth of 30 Hz can improve the Open-loop gain of the FSM control system compared to that achieved using the Q filter with a bandwidth of 15 Hz.

4. Performance of Anti-Shock Controller for FSM System

The simulated performance results of the DOB-based anti-shock controller for FSM control systems revealed that the target rotational position was maintained successfully at 0 μrad (i.e., neutral rotational position). When the 15 Hz bandwidth Q₂₀ and Q₃₁ filters were used in the DOB-based FSM control system, the RMS CES values were 100.1 and 88.8 μrad, respectively. Furthermore, when the 30 Hz bandwidth Q₂₀ and Q₃₁ filters were used in the DOB-based FSM control system, the RMS CES values were 74.9 and 63.9 μrad, respectively, as illustrated in Figure 10a,b. The overall simulated performance results of the DOB-based anti-shock controller for FSM control systems are summarized in

Table 2. Simulated performance results obtained using DOB-based anti-shock controller for FSM control systems.

Specification	PI Controller	Q20 Filter		Q31 Filter
		15 Hz	30 Hz	15 Hz	30 Hz
Minimum rotational position error (rms)	119.9 μrad	100.1 μrad	74.9 μrad	88.8 μrad	63.9 μrad
Reduced rate	-	16.5%	37.6%	25.9%	46.7%

.

The experimental performance results are presented in Figure 11. The experimental performance results of the DOB-based anti-shock controller for FSM control systems revealed that the target rotational position was maintained successfully at 0 μrad (i.e., neutral rotational position). According to Figure 11a, the root mean square (RMS) residual CES of the PI controller was 9.9 μrad. When the 15 Hz bandwidth Q₂₀ and Q₃₁ filters were used in the DOB-based FSM control system, the RMS CES values were 100.1 and 88.8 μrad, respectively, as illustrated in Figure 11b,c. Furthermore, when the 30 Hz bandwidth Q₂₀ and Q₃₁ filters were used in the DOB-based FSM control system, the RMS CES values were 74.9 and 63.9 μrad, respectively, as illustrated in Figure 11d,e.

Eventually, the disturbance-rejection performance in the DOB-based anti-shock controller for FSM systems improved as the order of the denominator and numerator increased, and as the bandwidth of the Q filter increased. The overall performance results of the DOB-based anti-shock controller for FSM control systems are summarized in

Table 3. Experimental performance results obtained using DOB-based anti-shock controller for FSM control systems.

Specification	PI Controller	Q20 Filter		Q31 Filter
		15 Hz	30 Hz	15 Hz	30 Hz
Minimum rotational position error (rms)	106.0 μrad	79.1 μrad	54.7 μrad	72.2 μrad	43.4 μrad
Reduced rate	-	25.3%	48.4%	31.9%	59.1%

. These results indicate that the performance of the proposed anti-shock controller was superior to that of the controller reported in previous studies [37,38].

5. Conclusions

In this study, we investigated how to improve the disturbance-rejection performance of an anti-shock controller for FSM systems by using a DOB to improve its tip-tilt control performance under external shocks. First of all, we analyzed the robustness of the DOB system quantitatively through the simulated performance of the DOB system. Also, the design parameters of the DOB system were experimentally derived.

Eventually, when the 15 Hz bandwidth Q₂₀ filter was used in the DOB-based anti-shock controller for FSM systems, the CES value decreased by 25.3% compared to that in the case without the DOB. Furthermore, when the 15 Hz bandwidth Q₃₁ filter was used in the DOB-based anti-shock controller for FSM systems, the CES value decreased by 31.9% compared to that in the case without the DOB. Furthermore, to improve the disturbance-rejection performance of the DOB-based anti-shock controller for FSM systems, the bandwidth of the Q₂₀ and Q₃₁ filters used therein was set to 30 Hz. The CES value decreased by approximately 48.4% and 59.1% when using the Q₂₀ and Q₃₁ filters, respectively, compared to that in the absence of the DOB.

These results indicate that the disturbance-rejection performance of the DOB-based control system improves as the order of the denominator and numerator of the Q filter increases, and as the bandwidth of the Q filter increases. Consequently, the proposed anti-shock controller performed efficiently in suppressing external disturbances in the FSM system.